Cascaded Lossless Commensurate Line Synthesis
Metin engül
Kadir Has University
Electronics Engineering Department
Cibali-Fatih, Istanbul, Turkey
msengul@khas.edu.tr
Abstract— In this paper, a synthesis algorithm for cascaded lossless commensurate lines is summarized. The algorithm is based on transfer matrix factorization. Firstly the characteristic impedance of the extracted element is calculated and then after extracting the element, the reflection factor of the remaining network is calculated. This process is repeated until the termination resistance is reached. An example is included, to illustrate the implementation of the algorithm.
Keywords-synthesis; commensurate lines; lossless networks
I.
I
NTRODUCTIONEspecially at microwave frequencies, distributed element
networks are preferred. In lots of microwave filter and
matching network designs, finite homogenous transmission
lines of commensurate lengths have been used [1, 2]. This
approach is based on that the distributed networks composed
of commensurate lengths of transmission lines could be
regarded as lumped element networks under the
transformation [3],
)
tanh(
τ
λ
=
p
(1)
where
p
=
σ
+
j
ω
is the complex frequency and
τ
is the
commensurate delay of the transmission line.
In literature, characteristic impedance of the extracted
commensurate line is calculated by using the following
formula [4], if
S
(
λ
)
is the given reflection factor,
)
1
(
1
)
1
(
1
1S
S
Z
−
+
=
(2)
Then, the reflection factor of the remaining network is [4]
λ
λ
λ
λ
λ
=
−
−
−
+
1
1
)
1
(
)
(
1
)
1
(
)
(
)
(
S
S
S
S
S
R.
(3)
As can be seen from Eq. (3), to get a degree reduction, the
denominator must has a root at
λ
=
−
1
, and numerator at
1
+
=
λ
. But in the new method, there is no need to find roots
at 1
λ
=
±
, to get a degree reduction.
In literature, many researches have been worked on the
analysis [5-8] and synthesis problem [9-17] of
distributed-element networks. For instance in [18], a transformation is
proposed, in [19], input impedance function is utilized in
synthesis process. But in the synthesis method presented here,
the network is thought as a lossless, reciprocal two-port
expressed in Belevitch form [20], and directly the reflection
factor is used.
In [21], the synthesis algorithm presented here has been
proposed. But when the number of transmission lines is
increased, the coefficients used in the algorithm get larger. So
a coefficient normalization step must be inserted to get more
precise element values. In the updated algorithm presented in
this paper, this coefficient normalization step has been
included.
In the following section, transfer matrix factorization is
explained briefly. Then, the modified synthesis algorithm is
given. Finally, an example is presented, to illustrate the
implementation of the algorithm.
II.
T
RANSFERM
ATRIXF
ACTORIZATIONCanonic form of the scattering transfer matrix
{ }
T of a
lossless, reciprocal two-port is defined as [1],
»
¼
º
«
¬
ª
=
g
h
h
g
f
T
* *1
μ
μ
,
(4)
where
=
*=
±
1
f
f
μ
is a unimodular constant, g is a strictly
Hurwitz real polynomial. These polynomials satisfy the
Feldtkeller equation,
gg
*=
hh
*+
ff
*(where “*” represents
paraconjugation).
Fig. 1. Cascade decomposition of a two-port.
It is desired to decompose the lossless, reciprocal two-port
{ }
N into two cascade connected lossless two-ports
{
N ,
aN
b}
which are also lossless and reciprocal (Fig. 1). This means to
factor the scattering transfer matrix
{ }
T into a product of two
scattering transfer matrices,
a
N
N
bN
R
T
978-1-4244-3896-9/09/$25.00 ©2009 IEEE
295
b a
T
T
T
=
⋅
,
(5a)
where
¸¸¹
·
¨¨©
§
=
a a a a a a a ag
h
h
g
f
T
* *1
μ
μ
and
¸¸¹
·
¨¨©
§
=
b b b b b b b bg
h
h
g
f
T
* *1
μ
μ
. (5b)
The polynomials
{
g
a,
h
a,
f
a}
and
{
g
b,
h
b,
f
b}
have the
same properties as
{
g
,
h
,
f
}
, and must satisfy the Feldtkeller
equation. Namely,
b a a b ag
h
h
g
g
=
+
μ
*,
(6a)
b a a b ag
g
h
h
h
=
+
μ
*,
(6b)
b af
f
f
=
,
(6c)
b aμ
μ
μ
=
.
(6d)
So if one writes
T
b=
T
a−1T
, two equations can be reached
as,
* a a a a a bf
f
gh
hg
h
μ
−
=
,
(7a)
* * * a a a a bf
f
hh
gg
g
=
−
.
(7b)
Now, the problem is to solve (7) in the unknown
polynomials
{
g
a,
h
a,
g
b,
h
b}
subject to the Feldtkeller
equation with
g
aand
g
bbeing strictly Hurwitz polynomials.
The problem has been solved by Fettweis by using a
modified formulation of the factorization problem [22, 23]. In
[23], a different set of equations are chosen as the basis for the
solution instead of solving (7).
III. A
LGORITHMFig. 2 Commensurate line extraction.
Consider the circuit shown in Fig. 2.
g
(λ
)
,
h
(λ
)
and
)
(
λ
f
polynomials are given as follows,
n n g g g g g(
λ
)= 0+ 1λ
+ 2λ
2+!+λ
, (8a)
n nh
h
h
h
h
(
λ
)
=
0+
1λ
+
2λ
2+
!
+
λ
,
(8b)
2 / 2)
1
(
)
(
nf
λ
=
−
λ
.
(8c)
Characteristic impedance
Z
1of the first commensurate line
can be calculated as,
)
1
(
)
1
(
)
1
(
)
1
(
1h
g
h
g
Z
−
+
=
.
(9)
Then,
g
(
λ
)
,
h
(
λ
)
and
f
(
λ
)
polynomials of the remaining
network are obtained as,
¦
= −=
n j j jD
g
1 1)
(
λ
λ
,
(10a)
¦
= −=
n j j jN
h
1 1)
(
λ
λ
, (10b)
2 / ) 1 ( 2)
1
(
)
(
=
−
n−f
λ
λ
,
(10c)
where
¦
=−
+=
j i i j i jy
D
1)
1
(
,
j=1,2,!,n,
(11a)
¦
==
j i i jx
N
1,
j=1,2,!,n,
(11b)
where
)
1
(
)
1
(
1 1g
g
h
h
x
i=
i−−
i−,
i=1,2,!,n,
(12a)
)
1
(
)
1
(
1 1g
h
h
g
y
i=
i−−
i−,
i=1,2,!,n. (12b)
The coefficients of the polynomials found in (10) may be
very large after a few elements are extracted. In the next steps
this cause to work with large numbers. As a result, element
values may not be calculated. So at this step coefficients must
be normalized.
The extraction of commensurate lines is implemented in a
similar fashion until the termination resistance (
R ) is reached.
IV.
E
XAMPLEExample given in [18] is solved, to illustrate the
implementation of the proposed algorithm. The given input
reflection factor is
)
(
)
(
)
(
λ
λ
λ
g
h
S
=
where
0211 . 0 316 . 0 29 . 2 31 . 10 76 . 33 44 . 79 6 . 152 7 . 206 8 . 248 9 . 167 7 . 121 ) ( 0105 . 0 165 . 0 298 . 1 072 . 6 75 . 21 45 . 52 8 . 111 8 . 151 2 . 209 2 . 136 7 . 121 ) ( 2 3 4 5 6 7 8 9 10 2 3 4 5 6 7 8 9 10 + + + + + + + + + + = + − + − + − + − + − = λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ g hStep 1
:
)
(
)
(
) 1 (λ
λ
h
h
=
and
g
(1)(
λ
)
=
g
(
λ
)
.
Step 2 :
2632 . 1 ) 1 ( ) 1 ( ) 1 ( ) 1 ( ) 1 ( ) 1 ( ) 1 ( ) 1 ( 1 = − + = h g h g Z 1Z
Z
2Z
nR
)
(
),
(
),
(
λ
h
λ
f
λ
g
296
Step 3 :
159440 0715 . 119 9 . 167 8 . 1023 2 . 136 ) 1 ( ) 1 ( 184560 0715 . 119 8 . 248 8 . 1023 2 . 209 ) 1 ( ) 1 ( 180030 0715 . 119 7 . 206 8 . 1023 8 . 151 ) 1 ( ) 1 ( 96295 0715 . 119 6 . 152 8 . 1023 8 . 111 ) 1 ( ) 1 ( 63159 0715 . 119 44 . 79 8 . 1023 45 . 52 ) 1 ( ) 1 ( 18249 0715 . 119 76 . 33 8 . 1023 75 . 21 ) 1 ( ) 1 ( 4 . 7444 0715 . 119 31 . 10 8 . 1023 072 . 6 ) 1 ( ) 1 ( 3 . 1056 0715 . 119 29 . 2 8 . 1023 298 . 1 ) 1 ( ) 1 ( 5597 . 206 0715 . 119 316 . 0 8 . 1023 165 . 0 ) 1 ( ) 1 ( 2379 . 8 0715 . 119 0211 . 0 8 . 1023 0105 . 0 ) 1 ( ) 1 ( ) 1 ( 9 ) 1 ( 9 10 ) 1 ( 8 ) 1 ( 8 9 ) 1 ( 7 ) 1 ( 7 8 ) 1 ( 6 ) 1 ( 6 7 ) 1 ( 5 ) 1 ( 5 6 ) 1 ( 4 ) 1 ( 4 5 ) 1 ( 3 ) 1 ( 3 4 ) 1 ( 2 ) 1 ( 2 3 ) 1 ( 1 ) 1 ( 1 2 ) 1 ( 0 ) 1 ( 0 1 − = ⋅ − ⋅ − = − = = ⋅ − ⋅ = − = − = ⋅ − ⋅ − = − = = ⋅ − ⋅ = − = − = ⋅ − ⋅ − = − = = ⋅ − ⋅ = − = − = ⋅ − ⋅ − = − = = ⋅ − ⋅ = − = − = ⋅ − ⋅ − = − = = ⋅ − ⋅ = − = h g g h x h g g h x h g g h x h g g h x h g g h x h g g h x h g g h x h g g h x h g g h x h g g h x 188120 0715 . 119 2 . 136 8 . 1023 9 . 167 ) 1 ( ) 1 ( 229820 0715 . 119 2 . 209 8 . 1023 8 . 248 ) 1 ( ) 1 ( 229700 0715 . 119 8 . 151 8 . 1023 7 . 206 ) 1 ( ) 1 ( 142930 0715 . 119 8 . 111 8 . 1023 6 . 152 ) 1 ( ) 1 ( 87579 0715 . 119 45 . 52 8 . 1023 44 . 79 ) 1 ( ) 1 ( 31975 0715 . 119 75 . 21 8 . 1023 76 . 33 ) 1 ( ) 1 ( 11279 0715 . 119 072 . 6 8 . 1023 31 . 10 ) 1 ( ) 1 ( 2190 0715 . 119 298 . 1 8 . 1023 29 . 2 ) 1 ( ) 1 ( 1793 . 343 0715 . 119 165 . 0 8 . 1023 316 . 0 ) 1 ( ) 1 ( 3527 . 20 0715 . 119 0105 . 0 8 . 1023 0211 . 0 ) 1 ( ) 1 ( ) 1 ( 9 ) 1 ( 9 10 ) 1 ( 8 ) 1 ( 8 9 ) 1 ( 7 ) 1 ( 7 8 ) 1 ( 6 ) 1 ( 6 7 ) 1 ( 5 ) 1 ( 5 6 ) 1 ( 4 ) 1 ( 4 5 ) 1 ( 3 ) 1 ( 3 4 ) 1 ( 2 ) 1 ( 2 3 ) 1 ( 1 ) 1 ( 1 2 ) 1 ( 0 ) 1 ( 0 1 = ⋅ + ⋅ = − = = ⋅ − ⋅ = − = = ⋅ + ⋅ = − = = ⋅ − ⋅ = − = = ⋅ + ⋅ = − = = ⋅ − ⋅ = − = = ⋅ + ⋅ = − = = ⋅ − ⋅ = − = = ⋅ + ⋅ = − = = ⋅ − ⋅ = − = h h g g y h h g g y h h g g y h h g g y h h g g y h h g g y h h g g y h h g g y h h g g y h h g g yStep 4 :
110110 2379 . 8 5597 . 206 3 . 1056 4 . 7444 18249 63159 96295 180030 184560 159440 49329 2379 . 8 5597 . 206 3 . 1056 4 . 7444 18249 63159 96295 180030 184560 135230 2379 . 8 5597 . 206 3 . 1056 4 . 7444 18249 63159 96295 180030 44798 2379 . 8 5597 . 206 3 . 1056 4 . 7444 18249 63159 96295 51497 2379 . 8 5597 . 206 3 . 1056 4 . 7444 18249 63159 11662 2379 . 8 5597 . 206 3 . 1056 4 . 7444 18249 4 . 6586 2379 . 8 5597 . 206 3 . 1056 4 . 7444 9450 . 857 2379 . 8 5597 . 206 3 . 1056 3218 . 198 2379 . 8 5597 . 206 2379 . 8 1 2 3 4 5 6 7 8 9 10 10 1 2 3 4 5 6 7 8 9 9 1 2 3 4 5 6 7 8 8 1 2 3 4 5 6 7 7 1 2 3 4 5 6 6 1 2 3 4 5 5 1 2 3 4 4 1 2 3 3 1 2 2 1 1 − = + − + − + − + − + − = + + + + + + + + + = = + − + − + − + − = + + + + + + + + = − = + − + − + − + − = + + + + + + + = = + − + − + − = + + + + + + = − = + − + − + − = + + + + + = = + − + − = + + + + = − = + − + − = + + + = = + − = + + = − = + − = + = = = x x x x x x x x x x N x x x x x x x x x N x x x x x x x x N x x x x x x x N x x x x x x N x x x x x N x x x x N x x x N x x N x N 110090 3527 . 20 1793 . 343 2190 11279 31975 87579 142930 229700 229820 188120 78029 3527 . 20 1793 . 343 2190 11279 31975 87579 142930 229700 229820 151790 3527 . 20 1793 . 343 2190 11279 31975 87579 142930 229700 77910 3527 . 20 1793 . 343 2190 11279 31975 87579 142930 65016 3527 . 20 1793 . 343 2190 11279 31975 87579 22563 3527 . 20 1793 . 343 2190 11279 31975 6 . 9411 3527 . 20 1793 . 343 2190 11279 2 . 1867 3527 . 20 1793 . 343 2190 8266 . 322 3527 . 20 1793 . 343 3527 . 20 1 2 3 4 5 6 7 8 9 10 10 1 2 3 4 5 6 7 8 9 9 1 2 3 4 5 6 7 8 8 1 2 3 4 5 6 7 7 1 2 3 4 5 6 6 1 2 3 4 5 5 1 2 3 4 4 1 2 3 3 1 2 2 1 1 = − + − + − + − + − = − + − + − + − + − = = + − + − + − + − = + − + − + − + − = = − + − + − + − = − + − + − + − = = + − + − + − = + − + − + − = = − + − + − = − + − + − = = + − + − = + − + − = = − + − = − + − = = + − = + − = = − = − = = = y y y y y y y y y y D y y y y y y y y y D y y y y y y y y D y y y y y y y D y y y y y y D y y y y y D y y y y D y y y D y y D y D297
Step 5 :
9 8 7 6 5 4 3 2 9 10 8 9 7 8 6 7 5 6 4 5 3 4 2 3 2 1 ) 2 ( 110090 78029 151790 77910 65016 22563 6 . 9411 2 . 1867 8266 . 322 2327 . 20 ) ( λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ + + + + + + + + + = + + + + + + + + + = D D D D D D D D D D g 9 8 7 6 5 4 3 2 9 10 8 9 7 8 6 7 5 6 4 5 3 4 2 3 2 1 ) 2 ( 110110 49329 135230 44798 51497 11662 4 . 6586 9450 . 857 3218 . 198 2379 . 8 ) ( λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ λ − + − + − + − + − = + + + + + + + + + = N N N N N N N N N N hAs can be seen from the expressions of
g
(2)(
λ
)
and
)
(
) 2 (λ
h
, the coefficients are very large even at the first step. If
the process is repeated, the coefficients will be much larger
and it will be impossible to work with these larger numbers.
Only seven elements can be extracted in this manner. So at
this step, the coefficients must be normalized. After
normalizing and applying the algorithm until the termination
resistance (
R ) is reached, the following impedance values are
obtained
.
9811
.
2
3431
.
0
,
9743
.
2
,
3453
.
0
,
9046
.
2
,
3564
.
0
7783
.
2
,
3876
.
0
,
3295
.
2
,
5662
.
0
,
2632
.
1
10 9 8 7 6 5 4 3 2 1=
=
=
=
=
=
=
=
=
=
=
R
Z
Z
Z
Z
Z
Z
Z
Z
Z
Z
Characteristic impedances found in [18] are
.
9779
.
2
343
.
0
,
97
.
2
,
346
.
0
,
92
.
2
,
355
.
0
79
.
2
,
387
.
0
,
33
.
2
,
566
.
0
,
26
.
1
10 9 8 7 6 5 4 3 2 1=
=
=
=
=
=
=
=
=
=
=
R
Z
Z
Z
Z
Z
Z
Z
Z
Z
Z
V.
C
ONCLUSIONThe proposed algorithm in [21] is a simple and powerful
method, but can cause large polynomial coefficients, as the
number of commensurate lines increases. So it needs a
modification; at each step the coefficients must be normalized
to be able to calculate all characteristic impedances. As a
result, a very simple to implement commensurate line synthesis
algorithm is obtained.
A
CKNOWLEDGMENTFruitful discussions with S.B. Yarman (Istanbul) are
gratefully acknowledged.
R
EFERENCES[1] A. Aksen. “Design of lossless two-port with mixed, lumped and distributed elements for broadband matching,” Ph.D. dissertation, Bochum, Ruhr University, 1994.
[2] A. Sertba. Genelletirilmi iki-kapl, iki-deikenli kaypsz merdiven devrelerin tanmlanmas, Ph.D. dissertation (in Turkish), stanbul, stanbul University, 1997.
[3] P. I. Richards, “Resistor-termination-line circuits,” Proc. IRE, vol. 36, pp. 217-220, Feb. 1948.
[4] H. J. Carlin, “Distributed circuit design with transmission line elements,” Proc. IEEE. vol. 59, no. 7, pp. 1059-1081, July 1971. [5] P. S. Castro and W. W. Happ, Distributed parameter circuits and
microsystem electronics, Proc. NEC, pp. 448-461, 1960.
[6] M. J. Hellstrom, “Equivalent distributed RC networks or transmission lines,” IRE Trans. Circuit Theory, vol. CT-9, pp. 247-251, Sept. 1962. [7] M. R. Wohlers, Lumped and distributed passive networks, a generalized
and advanced viewpoint. New York and London: Academic Press, 1969.
[8] M. Ghausi and J. Kelly, Introduction to distributed-parameter networks. New York: Krieger, 1977.
[9] K. Heizer, “Distributed RC networks with rational transfer functions,”
IRE Trans. Circuit Theory, vol. CT-9, pp. 356-362, Dec. 1962.
[10] R. W. Wyndrum, Jr., The exact synthesis of distributed RC networks, Dept. of Elec. Eng., New York University, N. Y., Tech. Rept. 400-476, May 1963.
[11] J. O. Scanlan and J. D. Rhodes, “Realizability and synthesis of a restricted class of distributed RC networks,” IEEE Trans. Circuit
Theory, vol. CT-12, no. 4, pp. 577-585, Dec. 1965.
[12] R. P. O’Shea, “Synthesis using distributed RC networks,” IEEE Trans.
Circuit Theory, vol. CT-12, no. 4, pp. 546-554, Dec. 1965.
[13] S. S. Penbeci and S. C. Lee, “Synthesis of distributed RC networks by means of orthogonal functions,” IEEE Trans. Circuit Theory, pp. 137-140, Feb. 1969.
[14] J. O. Scanlan and N. Ramamurty, “Cascade synthesis of distributed RC networks,” IEEE Trans. Circuit Theory, vol. CT-16, no. 1, pp. 47-57, Feb. 1969.
[15] S. C. Lee and S. S. Penbeci, “Computer-aided design of distributed RC networks,” IEEE Trans. Circuit Theory, vol. CT-17, no. 2, pp. 224-232, May 1970.
[16] P. Sotiriadis and Y. Tsividis, “Integrators using a single distributed RC elements,” IEEE International Symp. on Circuit and Systems 2002, vol. 2, pp. 21-24, May. 2002.
[17] P. Sotiriadis and Y. Tsividis, “Single-URC integrators,” IEEE Trans.
Circuit and System-I, vol. 50, no. 2, pp. 304-307, Feb. 2003.
[18] J. Komiak and H. J. Carlin, “Improved accuracy for commensurate-line synthesis,” IEEE Trans. Microwave Theory and Techniques, pp. 212-215, Apr. 1976.
[19] M. Hyder Ali and R. Yarlagadda, “A note on the unit element synthesis,” IEEE Trans. Circuit and Systems, vol. cas-25, no. 3, pp. 172-174, March 1978.
[20] V. Belevitch. Classical network theory. San Francisco, CA: Holden Day; 1968.
[21] M. engül, “Synthesis of cascaded lossless commensurate lines,” IEEE Trans. Circuit and Systems: Express Briefs, vol: 55, no: 1, pp: 89-91, Jan. 2008.
[22] A. Fettweis, “Factorization of transfer matrices of lossless two-ports,”
IEEE Trans. Circuit Theory, vol. 17, pp. 86-94, Feb. 1970.
[23] A. Fettweis, Cascade synthesis of lossless two-ports by transfer matrix
factorization, in R.Boite, ed., Network Theory, Gordon & Breach, 1972,
pp. 43-103.